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lt1223 1 1223fb typical applicatio u applicatio s u descriptio u features 100mhz current feedback amplifier 100mhz bandwidth at a v = 1 1000v/ s slew rate wide supply range: 5v to 15v 1mv input offset voltage 1 a input bias current 5m ? input resistance 75ns settling time to 0.1% 50ma output current 6ma quiescent current available in 8-lead plastic dip and so packages video amplifiers buffers if and rf amplification cable drivers 8-, 10-, 12-bit data acquisition systems the lt 1223 is a 100mhz current feedback amplifier with very good dc characteristics. the lt1223? high slew rate, 1000v/ s, wide supply range, 15v, and large output drive, 50ma, make it ideal for driving analog signals over double-terminated cables. the current feedback amplifier has high gain bandwidth at high gains, unlike conventional op amps. the lt1223 comes in the industry standard pinout and can upgrade the performance of many older products. the lt1223 is manufactured on linear technology? proprietary complementary bipolar process. video cable driver voltage gain vs frequency , ltc and lt are registered trademarks of linear technology corporation. all other trademarks are the property of their respective owners. ? in v out v r g 1k r f 1k 75 75 cable ? 75 ? + lt1223 lt1223 ?ta02 a = 1 + v r f r g at amplifier output 6db less at v out frequency (hz) 100k ?0 voltage gain (db) ?0 10 20 50 60 10m 100m 1g lt1223 ?tpc01 1m 0 30 40 100mhz gain bandwidth r g = 10 r g = 33 r g = 110 r g = 470 r g = 1k r g +
lt1223 2 1223fb order part number absolute axi u rati gs w ww u (note 1) j8 package 8-lead ceramic dip t jmax = 175 c, ja = 100 cw (j8) wu u package / o rder i for atio s8 part marking lt1223cn8 lt1223cs8 1223 t j max = 150 c, ja = 100 c/w(n8) t j max = 150 c, ja = 150 c/w(s8) obsolete package consider the n8 or s8 for alternative source supply voltage ...................................................... 18v differential input voltage ......................................... 5v input voltage ............................ equal to supply voltage output short circuit duration (note 2) ......... continuous operating temperature range lt1223m (obsolete) .............. ?5 c to 125 c lt1223c ................................................ 0 c to 70 c storage temperature range ..................65 c to 150 c junction temperature plastic package ........... 150 c junction temperature ceramic package (obsolete) ..................................... 175 c lead temperature (soldering, 10 sec.)................. 300 c lt1223cj8 lt1223mj8 consult ltc marketing for parts specified with wider operating temperature ranges. 1 2 3 4 8 7 6 5 top view null ?n +in v shutdown v + out null n8 package 8-lead plastic dip s8 package 8-lead plastic so electrical characteristics lt1223m/c symbol parameter conditions min typ max units v os input offset voltage v cm = 0v 1 3mv i in + noninverting input current v cm = 0v 1 3 a i in inverting input current v cm = 0v 1 3 a e n input noise voltage density f = 1khz, r f = 1k, r g = 10 ? 3.3 nv/ hz i n input noise current density f = 1khz, r f = 1k, r g = 10 ? 2.2 pa/ hz r in input resistance v in = 10v 1 10 m ? c in input capacitance 1.5 pf input voltage range 10 12 v cmrr common mode rejection ratio v cm = 10v 56 63 db inverting input current common mode rejection v cm = 10v 30 100 na/v psrr power supply rejection ratio v s = 4.5v to 18v 68 80 db noninverting input current power supply rejection v s = 4.5v to 18v 12 100 na/v inverting input current power supply rejection v s = 4.5v to 18v 60 500 na/v a v large signal voltage gain r load = 400 ? , v out = 10v 70 89 db r ol transresistance, ? v out / ? i in ? load = 400 ? , v out = 10v 1.5 5 m ? v out maximum output voltage swing r load = 200 ? 10 12 v i out maximum output current r load = 200 ? 50 60 ma sr slew rate r f = 1.5k, r g = 1.5k (note 3) 800 1300 v/ s bw bandwidth r f = 1k, r g = 1k, v out = 100mv 100 mhz v s = 15v, t a = 25 c, unless otherwise noted. order options tape and reel: add #tr lead free: add #pbf lead free tape and reel: add #trpbf lead free part marking: http://www.linear.com/leadfree/
lt1223 3 1223fb electrical characteristics lt1223m/c symbol parameter conditions min typ max units t r rise time r f = 1.5k, r g = 1.5k, v out = 1v 6.0 ns t pd propagation delay r f = 1.5k, r g = 1.5k, v out = 1v 6.0 ns overshoot r f = 1.5k, r g = 1.5k, v out = 1v 5 % t s settling time, 0.1% r f = 1k, r g = 1k, v out = 10v 75 ns differential gain r f = 1k, r g = 1k, r l = 150 ? 0.02 % differential phase r f = 1k, r g = 1k, r l = 150 ? 0.12 deg r out open-loop output resistance v out = 0, i out = 0 35 ? i s supply current v in = 0v 6 10 ma supply current, shutdown pin 8 current = 200 a24ma v s = 15v, t a = 25 c, unless otherwise noted. lt1223c symbol parameter conditions min typ max units v os input offset voltage v cm = 0v 1 3mv i in + noninverting input current v cm = 0v 1 3 a i in inverting input current v cm = 0v 1 3 a r in input resistance v in = 10v 110 m ? input voltage range 10 12 v cmrr common mode rejection ratio v cm = 10v 56 63 db inverting input current common mode rejection v cm = 10v 30 100 na/v psrr power supply rejection ratio v s = 4.5v to 18v 68 80 db noninverting input current power supply rejection v s = 4.5v to 18v 12 100 na/v inverting input current power supply rejection v s = 4.5v to 18v 60 500 na/ v a v large-signal voltage gain r load = 400 ? , v out = 10v 70 89 db r ol transresistance, ? v out / ? i in ? load = 400 ? , v out = 10v 1.5 5 m ? v out maximum output voltage swing r load = 200 ? 10 12 v i out maximum output current r load = 200 ? 50 60 ma i s supply current v in = 0v 610 ma supply current, shutdown pin 8 current = 200 a 24 ma the denotes the specifications which apply over the full operating temperature range, otherwise specifications are at v s = 15v, v cm = 0v, 0 c t a 70 c, unless otherwise noted.
lt1223 4 1223fb lt1223m symbol parameter conditions min typ max units v os input offset voltage v cm = 0v 1 5mv i in + noninverting input current v cm = 0v 1 5 a i in inverting input current v cm = 0v 1 10 a r in input resistance v in = 10v 110 m ? input voltage range 10 12 v cmrr common mode rejection ratio v cm = 10v 56 63 db inverting input current common mode rejection v cm = 10v 30 100 na/v psrr power supply rejection ratio v s = 4.5v to 15v 68 80 db noninverting input current power supply rejection v s = 4.5v to 15v 12 200 na/v inverting input current power supply rejection v s = 4.5v to 15v 60 500 na/v a v large-signal voltage gain r load = 400 ? , v out = 10v 70 89 db r ol transresistance, ? v out / ? i in ? load = 400 ? , v out = 10v 1.5 5 m ? v out maximum output voltage swing r load = 200 ? 7 12 v i out maximum output current r load = 200 ? 35 60 ma i s supply current v in = 0v 610 ma supply current, shutdown pin 8 current = 200 a 24 ma note 1: absolute maximum ratings are those values beyond which the life of a device may be impaired. note 2: a heat sink may be required. note 3: noninverting operation, v out = 10v, measured at 5v. electrical characteristics the denotes the specifications which apply over the full operating temperature range, otherwise specifications are at v s = 15v, v cm = 0v, 55 c t a 125 c, unless otherwise noted.
lt1223 5 1223fb typical perfor a ce characteristics uw supply current vs supply voltage, supply current vs supply voltage output short circuit-current vs v in = 0 (operating) (shutdown) temperature input common mode limit vs temperature +i b vs common mode voltage i b vs common mode voltage output voltage swing vs output voltage swing vs v os vs common mode voltage load resistor supply voltage supply voltage ( v) 0 0 supply current (ma) 2 4 6 8 10 lt1223 ?tpc02 2 4 6 8 101214161820 ?5 c 25 c 125 c supply voltage ( v) 0 0 supply current (ma) 1 2 3 4 lt1223 ?tpc03 2 4 6 8 101214161820 125 c ?5 c pin 8 = 0v 25 c case temperature ( c) ?0 0 output short circuit current (ma) 30 100 lt1223 ?tpc04 ?5 0 25 50 75 100 125 10 20 40 50 60 70 80 90 temperature ( c) common mode range (v) 2 lt1223 ?tpc05 1 3 4 ? ? ? ? v = 15v s v = 5v s v = 15v s v = 5v s ?0 ?5 0 25 50 75 100 125 v + v common mode voltage (v) ?5 ? i b ( a) ? ? 1 3 5 lt1223 ?tpc06 ?0 ? 0 5 10 15 25 c 125 c ? ? 0 2 4 ?5 c v = 15v s common mode voltage (v) ?5 ?0 ? b ( a) ? ? 2 6 10 lt1223 tpc07 ?0 ? 0 5 10 15 125 c ? ? 0 4 8 ?5 c v = 15v s 25 c common mode voltage (v) ?5 ?0 v (mv) ?0 10 20 lt1223 ?tpc08 ?0 ? 0 5 10 15 ?5 ? 0 5 15 ?5 c 25 c 125 c os v = 15v s load resistor ( ) 100 ?0 output voltage swing (v) 15 20 1000 10000 lt1223 ?tpc09 ? ?5 ?0 ? 0 5 10 125 c v s = 15v 25 c, ?5 c 125 c 25 c, ?5 c supply voltage ( v) 0 ?0 output voltage swing (v) ?0 ? 10 20 lt1223 ?tpc10 2 4 6 8 101214161820 125 c ?5 0 5 15 25 c 25 c 125 c ?5 c ?5 c
lt1223 6 1223fb typical perfor a ce characteristics uw 3db bandwidth vs 3db bandwidth vs minimum feedback resistor vs feedback resistor supply voltage voltage gain maximum capacitive load vs open-loop voltage gain vs feedback resistor load resistor transimpedance vs load resistor spot noise voltage and current vs power supply rejection vs frequency frequency output impedance vs frequency feedback resistor (k ) 0 0 ?db bandwidth (mhz) 30 100 lt1223 ?tpc11 123 10 20 40 50 60 70 80 90 ? l s ? a = 2; r f = r g r = 100 ; v = 15v no capacitive load v supply voltage ( v) 0 0 ?db bandwidth (mhz) 30 100 lt1223 ?tpc12 51015 10 20 40 50 60 70 80 90 r f = 750 r f = 1k r f = 1.5k r f = 2k r f = r g a = 2 r = 100 t = 25 c v ? a l voltage gain (v/v) 0 100 feedback resistor ( ) 400 1000 lt1223 ?tpc13 20 40 60 200 300 500 600 700 800 900 10 30 50 ? 2db peaking 0db peaking v = 15v r = 100 s l feedback resistor (k ) 0 10 capacitive load (pf) 100 1k 10k 123 lt1223 ?tpc14 ? l s a = 2; r f = r g r = 100; v = 15v peaking < 5db v load resistor ( ) 100 40 open loop voltage gain (db) 100 1000 10000 lt1223 ?tpc15 ? 50 60 70 80 90 ?5 c 25 c 125 c v = 15v v = 10v s o load resistor ( ) 100 0 transimpedance (m ) 10 1000 10000 lt1223 ?tpc16 ? 1 2 3 5 ? 4 6 7 8 9 v = 15v v = 10v s o ?5 c 25 c 125 c frequency (hz) 10 1 spot noise (nv/ or pa/ ) 10 100 1000 100 1k 10k lt1223 ?tpc17 e n +i n ? n hz hz ? frequency (hz) 20 power supply rejection (db) 40 60 80 10k 1m 10m 100m lt1223 ?tpc18 0 100k negative positive v = 15v r f = 1k s frequency (hz) 0.1 magnitude of output impedance ( ) 1 10 100 10k 1m 10m 100m lt1223 ?tpc19 0.01 100k ? r f = r g = 3k v = 15v s r f = r g = 1k
lt1223 7 1223fb applicatio s i for atio wu u u typical perfor a ce characteristics uw does in a voltage feedback op amp, the closed-loop bandwidth does not change. this is because the equiva- lent gain bandwidth product of the current feedback am- plifier is set by the thevenin equivalent resistance at the inverting input and the internal compensation capacitor. by keeping r f constant and changing the gain with r g , the thevenin resistance changes by the same amount as the change in gain. as a result, the net closed-loop bandwidth of the lt1223 remains the same for various closed-loop gains. voltage gain and phase vs total harmonic distortion vs 2nd and 3rd harmonic frequency frequency distortion vs frequency noninverting amplifier settling noninverting amplifier settling inverting amplifier settling time to 10mv vs output step time to 1mv vs output step time vs output step current feedback basics the small-signal bandwidth of the lt1223, like all current feedback amplifiers, isn? a straight inverse function of the closed-loop gain. this is because the feedback resistors determine the amount of current driving the amplifier? internal compensation capacitor. in fact, the amplifier? feedback resistor (r f ) from output to inverting input works with internal junction capacitances of the lt1223 to set the closed-loop bandwidth. even though the gain set resistor (r g ) from inverting input to ground works with r f to set the voltage gain just like it frequency (hz) 1m ?0 voltage gain (db) ?5 5 20 10m 100m 1g lt1223 ?tpc20 r 1k l gain ?5 ?0 ?0 ? 0 10 15 phase shift (degrees) ?25 ?0 90 225 ?80 ?35 ?5 0 45 135 180 phase r = 100 l ? r 1k l r = 100 l ? v = 15v r f = r g = 1k s frequency (hz) total harmonic distortion (%) 0.01 0.1 10 1k 10k 100k lt1223 ?tpc21 0.001 100 thd v = 15v v = 7v r = 400 r f = r g =1k s o l rms ? frequency (mhz) 1 ?0 distortion (dbc) ?0 10 100 lt1223 ?tpc22 ?0 ?0 ?0 ?0 2nd 3rd v = 15v v = 2v p-p r = 100 r f = 1k a = 10db s o l v settling time (ns) 0 ?0 output step (v) ? 10 lt1223 ?tpc23 20 40 60 80 100 ? ? ? 0 2 4 6 8 to 10mv to 10mv v s l a = +1 r f = 1k v = 15v r = 1k settling time ( s) 0 ?0 output step (v) ? 10 lt1223 ?tpc24 12 ? ? ? 0 2 4 6 8 to 1mv to 1mv a = +1 r = 1k v = 15v r = 1k f s v l settling time (ns) 0 ?0 output step (v) ? 10 lt1223 ?tpc25 100 ? ? ? 0 2 4 6 8 to 1mv to 10mv a = ? r = 1k v = 15v r = 1k f s v 20 40 60 80 l to 10mv to 1mv
lt1223 8 1223fb applicatio s i for atio wu u u the curve on the first page shows the lt1223 voltage gain versus frequency while driving 100 ? , for five gain settings from 1 to 100. the feedback resistor is a constant 1k and the gain resistor is varied from infinity to 10 ? . shown for comparison is a plot of the fixed 100mhz gain bandwidth limitation that a voltage feedback amplifier would have. it is obvious that for gains greater than one, the lt1223 provides 3 to 20 times more bandwidth. it is also evident that second order effects reduce the bandwidth somewhat at the higher gain settings. feedback resistor selection because the feedback resistor determines the compensa- tion of the lt1223, bandwidth and transient response can be optimized for almost every application. to increase the bandwidth when using higher gains, the feedback resistor (and gain resistor) can be reduced from the nominal 1k value. the minimum feedback resistor versus voltage gain curve shows the values to use for 15v supplies. larger feedback resistors can also be used to slow down the lt1223 as shown in the 3db bandwidth versus feedback resistor curve. capacitive loads the lt1223 can be isolated from capacitive loads with a small resistor (10 ? to 20 ? ) or it can drive the capacitive load directly if the feedback resistor is increased. both techniques lower the amplifier? bandwidth about the same amount. the advantage of resistive isolation is that the bandwidth is only reduced when the capacitive load is present. the disadvantage of resistor isolation is that resistive loading causes gain errors. because the dc accuracy is not degraded with resistive loading, the de- sired way of driving capacitive loads, such as flash con- verters, is to increase the feedback resistor. the maximum capacitive load versus feedback resistor curve shows the value of feedback resistor and capacitive load that gives 5db of peaking. for less peaking, use a larger feedback resistor. power supplies the lt1223 may be operated with single or split supplies as low as 4v (8v total) to as high as 18v (36v total). it is not necessary to use equal value split supplies, how- ever, the offset voltage will degrade about 350 v per volt of mismatch. the internal compensation capacitor de- creases with increasing supply voltage. the ?db band- width versus supply voltage curve shows how this affects the bandwidth for various feedback resistors. generally, the bandwidth at 5v supplies is about half the value it is at 15v supplies for a given feedback resistor. the lt1223 is very stable even with minimal supply bypassing, however, the transient response will suffer if the supply rings. it is recommended for good slew rate and settling time that 4.7 f tantalum capacitors be placed within 0.5 inches of the supply pins. input range the noninverting input of the lt1223 looks like a 10m resistor in parallel with a 3pf capacitor until the common mode range is exceeded. the input impedance drops somewhat and the input current rises to about 10 a when the input comes too close to the supplies. eventually, when the input exceeds the supply by one diode drop, the base collector junction of the input transistor forward biases and the input current rises dramatically. the input current should be limited to 10ma when exceeding the supplies. the amplifier will recover quickly when the input is returned to its normal common mode range unless the input was over 500mv beyond the supplies, then it will take an extra 100ns. offset adjust output offset voltage is equal to the input offset voltage times the gain plus the inverting input bias current times the feedback resistor. for low gain applications (3 or less) a 10k ? pot connected to pins 1 and 5 with wiper to v + will trim the inverting input current ( 10 a) to null the output; it does not change the offset voltage very much. if the lt1223 is used in a high gain application, where input offset voltage is the dominate error, it can be nulled by pulling approximately 100 a from pin 1 or 5. the easy way to do this is to use a 10k ? pot between pin 1 and 5 with a 150k resistor from the wiper to ground for 15v supply applications. use a 47k resistor when operating on a 5v supply.
lt1223 9 1223fb shutdown pin 8 activates a shutdown control function. pulling more than 200ma from pin 8 drops the supply current to less than 3ma, and puts the output into a high impedance state. the easy way to force shutdown is to ground pin 8, using an open collector (drain) logic stage. an internal resistor limits current, allowing direct interfacing with no addi- tional parts. when pin 8 is open, the lt1223 operates normally. slew rate the slew rate of a current feedback amplifier is not inde- pendent of the amplifier gain configuration the way it is in a traditional op amp. this is because the input stage and the output stage both have slew rate limitations. inverting amplifiers do not slew the input and are therefore limited only by the output stage. high gain, noninverting amplifi- ers are similar. the input stage slew rate of the lt1223 is about 350v/ s before it becomes nonlinear and is en- hanced by the normally reverse-biased emitters on the input transistors. the output slew rate depends on the size of the feedback resistors. the peak output slew rate is about 2000v/ s with a 1k feedback resistor and drops proportionally for larger values. at an output slew rate of 1000v/ s or more, the transistors in the ?irror circuits will begin to saturate due to the large feedback currents. this causes the output to have slew induced overshoot and is somewhat unusual looking; it is in no way harmful or dangerous to the device. the photos show the lt1223 in a noninverting gain of three (r f = 1k, r g = 500 ? ) with a 20v peak-to-peak output slewing at 500v/ s, 1000v/ s and 2000v/ s. settling time the inverting amplifier settling time versus output step curve shows that the lt1223 will settle to within 1mv of final value in less than 100ns for all output changes of 10v or less. when operated as an inverting amplifier there is less than 500 v of thermal settling in the amplifier. however, when operating the lt1223 as a noninverting amplifier, there is an additional thermal settling compo- nent that is about 200 v for every volt of input common mode change. so a noninverting gain of one amplifier will output slew rate at 2000v/ s shows aberrations (see text) output slew rate of 1000v/ s output slew rate of 500v/ s 1223 a01 1223 a02 1223 a03 applicatio s i for atio wu u u
lt1223 10 1223fb have about 2.5mv thermal tail on a 10v step. unfortu- nately, reducing the input signal and increasing the gain always results in a thermal tail of about the same amount for a given output step. for this reason we show separate graphs of 10mv and 1mv non-inverting amplifier settling times. just as the bandwidth of the lt1223 is fairly constant for various closed-loop gains, the settling time remains constant as well. adjustable gain amplifier to make a variable gain amplifier with the lt1223, vary the value of r g . the implementation of r g can be a pot, a light controlled resistor, a fet, or any other low capacitance variable resistor. the value of r f should not be varied to change the gain. if r f is changed, then the bandwidth will be reduced at maximum gain and the circuit will oscillate when r f is very small. adjustable bandwidth amplifier because the resistance at the inverting input determines the bandwidth of the lt1223, an adjustable bandwidth circuit can be made easily. the gain is set as before with r f and r g ; the bandwidth is maximum when the variable resistor is at a minimum. accurate bandwidth limiting the lt1223 it is very common to limit the bandwidth of an op amp by putting a small capacitor in parallel with r f . do not put a small capacitor from the inverting input of a current feedback amplifier to anywhere else, especially not to the output. the capacitor on the inverting input will cause peaking or oscillations. if you need to limit the bandwidth of a current feedback amplifier, use a resistor and capacitor at the noninverting input (r1 and c1). this technique will also cancel (to a degree) the peaking caused by stray capacitance at the inverting input. unfortunately, this will not limit the output noise the way it does for the op amp. current feedback amplifier integrator since we remember that the inverting input wants to see a resistor, we can add one to the standard integrator circuit. this generates a new summing node where we can apply capacitive feedback. the lt1223 integrator has excellent large signal capability and accurate phase shift at high frequencies. applicatio s i for atio wu u u lt1223 ?ta03 + in v out v lt1223 r f r g lt1223 ?ta04 + in v out v lt1223 r f 5k r g lt1223 ?ta05 + in v out v lt1223 r f r g r1 r1 = 300 c1 ? c1 = 100pf bw = 5mhz lt1223 ?ta06 + in v out v lt1223 r f 1k c1 out v in v 1 sc1r1 = r1
lt1223 11 1223fb inverting input (a1) senses the shield and the non-invert- ing input (a2) senses the center conductor. since this amplifier does not load the cable (take care to minimize stray capacitance) and it rejects common mode hum and noise, several amplifiers can sense the signal with only one termination at the end of the cable. the design equations are simple. just select the gain you need (it should be two or more) and the value of the feedback resistor (typically 1k) and calculate r g1 and r g2 . the gain can be tweaked with r g2 and the cmrr with r g1 if needed. the bandwidth of the noninverting input signal is not reduced by the presence of the other amplifier, however, the inverting input signal bandwidth is reduced since it passes two amplifiers. the cmrr is good at high frequen- cies because the bandwidth of the amplifiers are about the same even though they do not necessarily operate at the same gain. summing amplifier (dc accurate) the summing amplifier is easily made by adding additional inputs to the basic inverting amplifier configuration. the lt1223 has no i os spec because there is no correlation between the two input bias currents. therefore, we will not improve the dc accuracy of the inverting amplifier by putting in the extra resistor in the noninverting input. difference amplifier the lt1223 difference amplifier delivers excellent performance if the source impedance is very low. this is because the common mode input resistance is only equal to r f + r g . video instrumentation amplifier this instrumentation amplifier uses two lt1223s to in- crease the input resistance to well over 1m. this makes an excellent ?oop through?or cable sensing amplifier if the cable driver the cable driver circuit is shown on the front page. when driving a cable it is important to properly terminate both ends if even modest high frequency performance is required. the additional advantage of this is that it isolates the capacitive load of the cable from the amplifier so it can operate at maximum bandwidth. applicatio s i for atio wu u u v = ? lt1223 ?ta07 + in v out v lt1223 + i1 v i2 v 1 r 2 r n r v v v i1 i2 in g1 g2 gn out f r r r + g g g r f () (r f ?50) lt1223 ?ta08 + out v lt1223 r f 100 v1 v2 optional trim for cmrr r g r g (v1 ?v2) r f r g v out = r g1 1k lt1223 ?ta09 out v a1 lt1223 in v a2 lt1223 in v ? + + r f1 1k r g2 1k r f2 1k v out = g (v in + ?v in ) r f1 = r f2 ; r g1 = (g ?1) r f2 ; r g2 = trim gain (g) with r g2 ; trim cmrr with r g1 r f2 g ?1
lt1223 12 1223fb typical applicatio u 150ma output current video amp sche atic w w si plified 75 ? 75 ? 75 ? 75 ? 75 ? 75 ? 75 ? 75 ? 75 ? lt1223 ?ta10 + lt1223 v in in lt1010 out v v 2k + 75 20 v + v 2k bias r = 2k to stabilize circuit differential gain = 1% differential phase = 1 f ? ? lt1223 ?ta01 bias 3 4 6 7 8 1 5 10k 15k bias 2
lt1223 13 1223fb package descriptio u j8 package 8-lead cerdip (narrow .300 inch, hermetic) (reference ltc dwg # 05-08-1110) obsolete package j8 0801 .014 ?.026 (0.360 ?0.660) .200 (5.080) max .015 ?.060 (0.381 ?1.524) .125 3.175 min .100 (2.54) bsc .300 bsc (7.62 bsc) .008 ?.018 (0.203 ?0.457) 0 ?15 .005 (0.127) min .405 (10.287) max .220 ?.310 (5.588 ?7.874) 12 3 4 87 65 .025 (0.635) rad typ .045 ?.068 (1.143 ?1.650) full lead option .023 ?.045 (0.584 ?1.143) half lead option corner leads option (4 plcs) .045 ?.065 (1.143 ?1.651) note: lead dimensions apply to solder dip/plate or tin plate leads
lt1223 14 1223fb n8 package 8-lead pdip (narrow .300 inch) (reference ltc dwg # 05-08-1510) package descriptio u n8 1002 .065 (1.651) typ .045 ?.065 (1.143 ?1.651) .130 .005 (3.302 0.127) .020 (0.508) min .018 .003 (0.457 0.076) .120 (3.048) min 12 3 4 87 6 5 .255 .015* (6.477 0.381) .400* (10.160) max .008 ?.015 (0.203 ?0.381) .300 ?.325 (7.620 ?8.255) .325 +.035 ?015 +0.889 0.381 8.255 () note: 1. dimensions are inches millimeters *these dimensions do not include mold flash or protrusions. mold flash or protrusions shall not exceed .010 inch (0.254mm) .100 (2.54) bsc
lt1223 15 1223fb s8 package 8-lead plastic small outline (narrow .150 inch) (reference ltc dwg # 05-08-1610) package descriptio u information furnished by linear technology corporation is believed to be accurate and reliable. however, no responsibility is assumed for its use. linear technology corporation makes no represen- tation that the interconnection of its circuits as described herein will not infringe on existing patent rights. .016 ?.050 (0.406 ?1.270) .010 ?.020 (0.254 ?0.508) 45 0 ?8 typ .008 ?.010 (0.203 ?0.254) so8 0303 .053 ?.069 (1.346 ?1.752) .014 ?.019 (0.355 ?0.483) typ .004 ?.010 (0.101 ?0.254) .050 (1.270) bsc 1 2 3 4 .150 ?.157 (3.810 ?3.988) note 3 8 7 6 5 .189 ?.197 (4.801 ?5.004) note 3 .228 ?.244 (5.791 ?6.197) .245 min .160 .005 recommended solder pad layout .045 .005 .050 bsc .030 .005 typ inches (millimeters) note: 1. dimensions in 2. drawing not to scale 3. these dimensions do not include mold flash or protrusions. mold flash or protrusions shall not exceed .006" (0.15mm)
lt1223 16 1223fb related parts part number description comments lt1206 250ma/60mhz current feedback amplifier 900v/ s, shutdown lt1395 400mhz current feedback amplifier 800v/ s, 4.6ma supply current, sot-23 package lt1497 dual 125ma, 50mhz current feedback amplifier 900v/ s, 7ma supply current lt6210/lt6211 single/dual programmable supply current, rail-to-rail c-load tm stable, 200mhz, 700v/ s output c-load is a trademark of linear technology corporation. linear technology corporation 1630 mccarthy blvd., milpitas, ca 95035-7417 (408) 432-1900 fax: (408) 434-0507 www.linear.com ? linear technology corporation 1992 lt/lt 0605 rev b ?printed in usa

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